Aggregation node for wireless access network utilizing hybrid beamforming

ABSTRACT

A high frequency data network access system leverages commodity WiFi chipsets and specifically multi spatial stream (e.g., 802.11 ac) chipsets in combination with phased array antenna systems at the aggregation nodes. Examples can be very spectrally efficient with both polarization and frequency diversity.

RELATED APPLICATIONS

This application claims the benefit under 35 USC 119(e) of U.S.Provisional Application No. 62/287,605, filed on Jan. 27, 2016, which isincorporated herein by reference in its entirety.

This application is related to U.S. application Ser. No. 15/418,256filed on Jan. 27, 2017, entitled “Star topology fixed wireless accessnetwork”, now U.S. Patent Publication No.: 2017/0215089 A1, U.S.application Ser. No. 15/418,291 filed on Jan. 27, 2017, entitled“Subscriber node for fixed wireless access network with steeredantenna”, now U.S. Patent Publication No.: 2017/0215090 A1, U.S.application Ser. No. 15/418,303 filed on Jan. 27, 2017, entitled “Highfrequency fixed wireless access network using multi spatial streamWiFi”, now U.S. Patent Publication No.: 2017/0215192 A1, and U.S.application Ser. No. 15/418,317 filed on Jan. 27, 2017, entitled “Nodesfor high frequency fixed wireless access network”, now U.S. PatentPublication No.: 2017/0215210 A1, all of which are incorporated hereinby reference in their entirety.

BACKGROUND OF THE INVENTION

Internet service providers (ISPs) have historically used a number ofdifferent technologies in their subscriber or access networks to delivernetwork connectivity to premises such as homes, multidwelling units, andbusinesses. Initially premises were connected via dial-up connectionsover POTS lines, or ISDN. Often businesses used T-1 to T-3 connections.

Nowadays, DSL, cable and optical fiber networks are common in urban andmetropolitan areas to provide network access.

Fixed wireless network access is another option in some areas. ISPsproviding the wireless network access can transmit and receive data toand from endpoint nodes usually at premises as radio waves viatransmission towers. This has been typically used in rural areas wherecable and optical fiber networks are not available.

SUMMARY OF THE INVENTION

The systems described herein can be generally utilized in frequencywireless data networks, typically operating in the 10 GHz to 300 GHzband for communications between aggregation nodes and one or more highfrequency endpoint nodes such as fixed subscriber nodes and/ormulti-dwelling unit nodes, usually in star-topology networks.Nevertheless, the technology also has application to mobile andsemi-mobile applications and point-to-points links. This spectral bandencompasses millimeter wavelengths (mm-wave) that are typicallydescribed as covering the 30 GHz to 300 GHz frequency band.

In many of the systems, the aggregation nodes have at least one phasedarray antenna that divides an area of coverage into multiple subsectors.In operation, the aggregation nodes transmit and receive high frequencymodulated carrier signals to and from the endpoint nodes. These nodesare associated with different subsectors in a preferablyazimuthal/horizontal fan pattern of the antennas. By forming beams forthese subsectors and towards a specific endpoint nodes or groups ofendpoint nodes, and/or simultaneously forming several beams to differentendpoint nodes within different subsectors from the same antenna, theaggregation node can communicate with the endpoint nodes, with lower orwithout interference between nodes. Another advantage of beam forming atthe aggregation node is power management for both the aggregation nodeand the endpoint nodes. Specifically, the transmission power on thedownlink from the aggregation node to the endpoint nodes is lowerbecause the aggregation node beam(s) are directed at individual endpointnodes or small groups of endpoint nodes. On the other hand, thetransmission power on the uplink from the endpoint nodes to theaggregation nodes can be lower since the aggregation node's antenna iselectronically directed at individual endpoint nodes or groups ofendpoint nodes.

In general, according to one aspect, the invention features anaggregation node for a wireless access system. The node comprises anantenna array system for transmitting high frequency signals to and/orreceiving high frequency signals from subscriber nodes, a phase controldevice coupled to the antenna array system via a set of feedlines, andan amplifier system for amplifying the feeds on the between the ante raysystem and the phase control device.

In embodiments, the antenna array system can include at least onetransmit antenna array for transmitting the high frequency signals tothe subscriber nodes and at least one receive antenna array forreceiving the high frequency signals from the subscriber nodes. Thephase control device can include one or more Rotman lens.

This phase control device controls phases of signals to be fed to theamplifier system and then to the phased array antenna system to directthe high frequency signals to different portions of an area of coverage.

In the receive side, the phase control device controls phases of signalsreceived from the antenna array system to direct high frequency signalsreceived from different portions of an area of coverage to differentoutput ports of the phase control device.

The amplifier system can comprise power amplifiers, possibly separatephase matched amplifiers, at ports of the phase control device.

In general, according to one aspect, the invention features acommunication method for an aggregation node and subscriber nodes in awireless access system. The method comprises generating high frequencysignals for different subscriber nodes, feeding the high frequencysignals into a transmit phase control device, amplifying feeds at theoutput ports of the transmit phase control device, and beaming the highfrequency signals to different subscriber nodes within an area ofcoverage.

The above and other features of the invention including various noveldetails of construction and combinations of parts, and other advantages,will now be more particularly described with reference to theaccompanying drawings and pointed out in the claims. It will beunderstood that the particular method and device embodying the inventionare shown by way of illustration and not as a limitation of theinvention. The principles and features of this invention may be employedin various and numerous embodiments without departing from the scope ofthe invention.

BRIEF DESCRIPTION OF THE DRAWINGS

In the accompanying drawings, reference characters refer to the sameparts throughout the different views. The drawings are not necessarilyto scale; emphasis has instead been placed upon illustrating theprinciples of the invention. Of the drawings:

FIGS. 1A-1C are block diagrams showing different deployments ofaggregation nodes and endpoint nodes in a fixed wireless access system;

FIGS. 2A-2B are perspective views of a subscriber endpoint node mountedat a window of a subscriber's premise;

FIG. 2C is a perspective view with housing components of the subscriberendpoint node shown in phantom;

FIG. 3A shows an example of a multiple dwelling unit endpoint nodelocated on a rooftop of a building;

FIG. 3B is a diagram of the mechanical arrangement of the multipledwelling unit endpoint node;

FIG. 4A is a block diagram that shows components of the subscriberendpoint node;

FIG. 4B is a block diagram that shows the components of the multipledwelling unit endpoint node;

FIG. 5 is schematic diagram showing a frequency plan utilized forwireless communications between the aggregation node and the endpointnodes according to one embodiment;

FIGS. 6A and 6B are block diagrams of a diplexer module for the endpointnode;

FIG. 7 is a block diagram that shows direct conversion between WiFi andhigh frequency signals at the endpoint node according to anotherembodiment;

FIGS. 8A-8B are a perspective view and a perspective exploded viewshowing an extremely high frequency (EHF) module of the endpoint node;

FIGS. 9A-9B are circuit diagrams of the EHF module of the endpoint node;

FIGS. 10A-10B are partial perspective views showing exemplary patchantenna arrays for the EHF module of the endpoint node;

FIG. 11A shows another example of a patch antenna array for the EHFmodule of the endpoint node;

FIG. 11B is a cross-sectional view of a patch antenna for the EHFmodule;

FIGS. 12A-12B show different feeding techniques for the patch antennaarrays at the endpoint node;

FIG. 13 shows a combined feeding technique for the patch antenna arraysat the endpoint node;

FIGS. 14A-14B are schematic drawings illustrating techniques forcoupling patch antenna arrays at the multiple dwelling unit endpointnode;

FIGS. 15A-15B are perspective views showing sector head of theaggregation node;

FIG. 16 is a block diagram showing two deployment examples for theaggregation node;

FIG. 17 is a block diagram showing components of a sector head of theaggregation node;

FIG. 18 is a schematic diagram for the aggregation node of a firstembodiment;

FIG. 19 is a block diagram showing a modem block for the sector head;

FIG. 20 is a circuit diagram for a transmit diplexer of a diplexer blockassociated with the sector head;

FIG. 21 is a block diagram for a receive diplexer of the diplexer block;

FIG. 22 is a block diagram showing a second embodiment of the componentsof the sector head of the aggregation node;

FIG. 23 is an exemplary schematic diagram for the aggregation node of asecond embodiment;

FIG. 24 is a circuit diagram for a quad block-up converter;

FIG. 25 is a circuit diagram for a quad block-down converter;

FIG. 26 is a circuit diagram showing a clock generator and a synthesizermodule;

FIG. 27 is a perspective view of a sector head of an aggregation nodewith a housing shown in phantom illustrating aspects of the mechanicallayout and layout of the antenna arrays;

FIGS. 28A-28B are a front plan scale view of a backplate and aperspective scale view of a front plate, respectively, showing anexemplary receive side of a phased array antenna system;

FIG. 28C-28D are a perspective scale view of an exemplary transmit sideof the phased array antenna system and its front plate, respectively;and

FIG. 29 is a schematic diagram for high frequency transmission at atransmit antenna array according to a different embodiment.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS

The invention now will be described more fully hereinafter withreference to the accompanying drawings, in which illustrativeembodiments of the invention are shown. This invention may, however, beembodied in many different forms and should not be construed as limitedto the embodiments set forth herein; rather, these embodiments areprovided so that this disclosure will be thorough and complete, and willfully convey the scope of the invention to those skilled in the art.

As used herein, the term “and/or” includes any and all combinations ofone or more of the associated listed items. Further, the singular formsand the articles “a”, “an” and “the” are intended to include the pluralforms as well, unless expressly stated otherwise. It will be furtherunderstood that the terms: includes, comprises, including and/orcomprising, when used in this specification, specify the presence ofstated features, integers, steps, operations, elements, and/orcomponents, but do not preclude the presence or addition of one or moreother features, integers, steps, operations, elements, components,and/or groups thereof. Further, it will be understood that when anelement, including component or subsystem, is referred to and/or shownas being connected or coupled to another element, it can be directlyconnected or coupled to the other element or intervening elements may bepresent.

A system 100 illustrated in FIG. 1A shows an aggregation node (AN) 102and a plurality of high frequency network endpoint nodes (EN) 104, e.g.,104-1, 104-2, . . . , and 104-n.

The aggregation node 102 utilizes a phased array antenna system 103 tocommunicate with the endpoint nodes 104-1-104-m. The antenna systempreferably covers an azimuthal arc of between about 90 degrees and 180degrees; with about 120 degrees currently being used.

The operation of the phased array antenna system 103 then divides theantenna's area of coverage into multiple subsectors S1, S2, . . . , Sn.In the illustrated example, the subsectors are distributed in anazimuthal fan, with the subsectors adjoining one another. There are atleast two subsectors; with some embodiments having four, eight or moresubsectors. As a result, in typical implementations, each subsectorcovers an azimuthal arc of between possibly 8 degrees and 60 degrees.Currently, the subsector arc is between about 10 degrees and 25 degrees.

The phased array antenna system 103 forms transmit and receive beamsB1-Bn that correspond to each of the subsectors. In this way, theaggregation node 102 reduces interference between endpoint nodes,conserves power on the downlinks and reduces transmit power requirementsby the endpoint nodes on the uplinks.

The endpoint nodes EN are distributed within and thereby associated withdifferent subsectors. For example, subscriber nodes 104-1-104-3 areassociated with subsector S1, subscriber nodes 104-4-104-6 areassociated with subsector S2, subscriber nodes 104-7-104-8 areassociated with subsector S3, and subscriber nodes 104-9 to 104-n areassociated with subsector S4.

In some embodiments, the phased array antenna system 103 produces anumber of beams for the subscriber node/group of subscriber nodes ineach subsector S1, S2, . . . , Sn. The phased array antenna system 103typically includes one or more transmit phased array antennas T fortransmitting data streams to the endpoint nodes 104 and one or morereceive phased array antennas R for receiving data streams from theendpoint nodes 104.

Each endpoint node 104 communicates with the aggregation node 102 bymeans of an electronic assembly or system that provides a wireless ISP(internet service provider) handoff at the premises where the endpointnode 104 is installed. The endpoint node 104 is a residential orbusiness fixed wireless endpoint that communicates with the aggregationnode 102 via high frequency network (i.e., using high frequencycommunication links/radios), In some embodiments, the high frequencynetwork operates between 10 and 300 GHz, or more commonly between about20 and 60 GHz.

Locally the endpoint node 104, in a typical residential implementation,communicates with a modem/router or access point over possibly a WiFitunnel (in the 2.4 or 5 GHz bands or the WiGig tri-band in the 2.4, 5and 60 GHz bands, or IEEE 802.11ac IEEE 802.11ad-2012) or via a wiredconnection (e.g., 1000BASE-T). This modem/router or access point thenmaintains the local area network at the subscriber's premises.

In other cases, the endpoint node 104 itself maintains the wired and/orwireless LAN at the premises. It provides typical functions associatedwith LAN routers, such as Network Address Translation (NAT), guestnetworks, Parental Controls and other Access Restrictions, VPN Serverand Client Support, Port Forwarding and UPnP, and DHCP (Dynamic HostConfiguration Protocol) server that automatically assigns IP addressesto network devices on the LAN.

According to a preferred embodiment, the aggregation node includesmultiple WiFi chipsets. These are commercially available systems of oneor more chips that implement the IEEE 802.11 standard. These chipsetsare capable of maintaining multiple spatial streams such as provided bythe IEEE 802.11n or 802.11ac versions and follow-on versions of thestandard. Each of these WiFi chipsets produce WiFi signals, which aresignals that have been encoded according to the IEEE 802.11 standard.These WiFi signals are then upconverted and transmitted to the endpointnodes 104. In turn, the endpoint nodes transmit high frequency signalsback, which signals are downconverted to WiFi signals at theconventional frequencies such as 2.4 or 5 GHz.

These WiFi chipsets are allocated to their own, one or more, subsectors.Further, their WiFi signals are also preferably up and down converted todifferent carrier frequencies to minimize inter-chipset interference.Thus, for example, WiFi chipset “a” might communicate with nodes insubsectors S1 and S2 at frequency F1, whereas WiFi chipset “b” mightcommunicate with nodes in subsectors S3 and S4 at frequency F2.

FIG. 1B illustrates the system 100 including the aggregation node 102with its phased array antenna system 103 providing access to a pluralityof multiple dwelling units (MDU) 106 (e.g., 106-1, 106-2, . . . 106-n).In this deployment example, the aggregation node 102 provides a wirelessISP handoff to the multiple dwelling units 106-1, 106-2, 106-n. Each ofthese multiple dwelling units 106 in turn includes multiple housingunits 120 such as apartments or condominiums (e.g., 120-1, 120-2, . . ., 120-6) which typically separately subscribe to the Internet service.In general, MDU is a classification of housing where multiple separatehousing units for residential inhabitants are contained within onebuilding or several buildings within one complex (e.g., an apartmentbuilding).

In the illustrated exemplary system 100, each multiple dwelling unit MDU106 (e.g., 106-1, 106-2) has one or more endpoint nodes, called multipledwelling unit nodes (MDNs). For example, multiple dwelling unit 106-1has two MDNs, MDNa-1, MDNb-1. Likewise multiple dwelling unit 106-2 hastwo MDNs, MDNa-2, MDNb-2. The advantage of having a number of multipledwelling nodes for each multiple dwelling unit is primarily redundancy.If one of the MDNs fails, then the second MDN can take over and providethe link to the aggregation node 102.

In the illustrated example, routers/switches SW-1, SW-2, SW-n arelocated between the MDNs for a particular multiple dwelling unit 106-1,106-n and the cabling that provides the wired connections to each of theseparate housing units 120, for example. In general, the switches SW-11,SW-2, SW-n monitor the health of the MDNs for the MDU 106 and willswitch off to a backup MDN in the case of the failure of the primaryMDN. In other cases, the switches SW-1, SW-2, SW-n load balancebandwidth between the MDNs in a situation where the MDNs connect todifferent aggregation nodes 102 to provide increased data throughput.

FIG. 1C shows another implementation of the system 100, where MDNs(e.g., MDNa-1, MDNb-1) for the respective MDU 106-1 connect to differentaggregation nodes 102 (e.g., 102-1, 102-2) via separate high frequencylinks 115. This can provide at least two advantages. Firstly, thisarrangement provides redundancy against the failure of a particularaggregation node 102. Secondly, throughput to and from the particularmultiple dwelling unit 106-1 can also be improved.

Here, a router/switch SW-1 is located between the MDNs (MDNa-1, MDNb-1)and the cabling 118-1 . . . 118-6 that provides wired connections toeach of the housing units 120-1, 120-2, . . . , 120-6. In someimplementations, the MDNs (MDNa-1, MDNb-1) couple to the switch SW-1 viaCategory 6 (cat 6) cabling 116 with Power over Ethernet (POE) or highpower POE. As a result, the MDN are powered using a common cablingsystem with data transmission. Other mechanisms for coupling the MDNs tothe SW-1 can be deployed without departing from the scope of theinvention.

Each floor in the MDU 106-1 will typically have a telephone (wiring)closet (i.e., three closets 125-1, 125-2, and 125-3 for the threefloors). In one implementation, Category 5e/category 6 cables 117 runbetween the telephone closets 125-1, 125-2, and 125-3, although othercabling/coupling means can be utilized. In one example, a G.hn switch(e.g., 126-1, 126-2, 126-3) is installed in each telephone closet. G.hnis a specification for home networking that operates over three types oflegacy wires: telephone wiring, coaxial cables, and power lines. TheG.hn specification allows data rates of up to 1 Gbit/s. The G.hnswitches 126-1, 126-2, 126-3 network over any of the supported wiretypes. In one implementation, the G.hn switches 126-1, 126-2, 126-3network over telephone line pairs or Category (cat 3) cable, or Category5 (cat) cable that serves as the final cabling runs 118-1 . . . 118-6 toeach unit 120-1 . . . 120-6, although other networking means can beutilized. In the illustrated example, the LAN for each unit 120-1 . . .120-6 is maintained by a wireless premises networking device/router110-1 . . . 110-6.

FIG. 2A shows an example of the endpoint node 104 mounted at a window ofa subscriber's premise, such as a residence.

This illustrated subscriber endpoint node 104 is designed forinstallation in a window of the residence. It has an outdoor unit (OM)202 coupled to an indoor unit (IDU) 204 by a bridge unit 206. Thisexemplary subscriber node 104 is mounted in the manner of a windowair-conditioning unit. Specifically, with the illustrated double hungwindow 200, the subscriber node 104 is placed on the windowsill and thenthe lower light of the double hung window 200 is closed against asealing member 208. In particular, a bottom rail 210 of the lower sashof the window 200 clamps the sealing member 208 against the window'ssill. This leaves the IDU 204 on the inside of the subscriber's premisesand the ODU 202 exposed on the outside of the subscriber's premises(i.e., outside the window 200). The bridge unit 206 extends through thesealing member 208 and mechanically supports both the ODU 202 and theIDU 204 on the windowsill 205, The bridge unit 206 provides structuralsupport for the assembly, as well as acts as a conduit for electricalcables between the ODU 202 and the IDU 204.

In other embodiments, the IDU 204 and ODU 202 are connected by one ormore cables, such as ribbon cables that extend under the closed window,but are otherwise physically separated, and can be detached from eachother.

The ODU 202 is configured for high frequency communications with theaggregation node 102, and the IDU 204 is configured for WiFicommunications (or wired connections or communications over anotherunlicensed band) with one or more devices inside the subscriber'spremise. In some embodiments, the IDU 204 can communicate with a routeraccess point or directly with one or more user devices at thesubscriber's premise. The bridge unit 206 includes one or moreinterconnection cables for coupling the ODU 202 with the IDU 204, and aDC power module, e.g., one that can be powered by a wall outlet.

On the other hand, in still other embodiments, the subscriber nodes 104are not separated into IDU 204, ODU 202, and bridge units 206. Instead,in one case, all of the necessary electronics are contained within asingle housing that is installed on an outer wall or window of thepremises. In one specific example, the electronics of the ODU 202 andIDU 204 are contained in weatherproof case, which then magneticallymounts to the glass or glazing of a window.

FIG. 2B shows the ODU 202 supported by the bridge unit 206 from avantage point outside of the subscriber's premises. The ODU 202 issupported by the bridge unit 206, which extends through the sealingmember 208.

In other examples, the IDU 204 is located inside the subscriber'spremises on the interior side of an outer wall or near an outer wall ofthe premises. The ODU 202 is located on an exterior side of the outerwall. For example, in some implementations, a hole is drilled throughthe outer wall such as in the attic of the premises. In other examples,a hole is drilled through the roof. Then, the ODU 202 is mounted on theoutside. The IDU 204 is mounted on an adjacent interior surface of theroof or wall, such as mounted between rafters or studs.

FIG. 2C is a diagram of the subscriber node 104, in which the enclosurecomponents of the subscriber node 104 are shown in phantom. The IDU 204coupled to the ODU 202 via the bridge unit 206 that projects through thesealing member 208. The IDU 204 includes a local wireless and/or wiredmodule 210 that maintains a wireless or wired local area network for thesubscriber's premises. In this case, the local wireless module 210directly transmits and receives information with network devices at thesubscriber's premise. In other cases, the local wireless module 210transmits and receives information with a local wireless accesspoint/router that then maintains the wireless local area network.

The ODU 202 includes an extremely high frequency (EHF) communicationmodule 220 (referred to hereinafter as an EHF module 220) that has oneor more integrated patch array antennas with transceivers. The EHFmodule 220 transmits and receives information in high frequency signalsto and from the aggregation node 102. A servo controlled motor unit 222supports and mechanically steers the EHF module 220 (i.e., steers thepatch array antennas of the EHF module 220). A weather hardenedenclosure (referred to as a “Radome”) 224 is designed for weather and UVprotection (i.e., to protect the EHF module 220 and motor unit 222 fromweather conditions) but is transparent to the high frequencies. In someembodiments, a heater (not shown) is also installed within the enclosure224. In some embodiments, the combination of the EHF module 220 and theservo controlled motor unit 222 can be referred to as a steerableantenna module.

The servo controlled motor unit 222 preferably includes a 2-axispan-tilt mount or gimbal that is controlled by one or more motors. Thepan-tilt mount is used to rotate the EHF module 220 so that theintegrated patch array antenna can be aligned for communicating with theaggregation node 102. Specifically, the motor unit 222 rotates the EHFmodule 220 around the vertical axis or in an azimuth direction andfurther tips the EHF module 220 around a horizontal axis or in theelevation direction. This movement allows the integrated patch arrayantenna of the EHF module 220 to be pointed at the phased array antennasystem 103 of the aggregation node 102. This movement also allows adynamic repositioning of the network without requiring site visits. Forexample, in the case of a failure of a particular aggregation node 102or the addition of a new aggregation node 102 to the overall localnetwork system (e.g., system 100), the EHF module 220 will automaticallyre-point to a secondary/backup/new aggregation node 102. Additionally,in the case of a site that is served by multiple aggregation nodes 102,a separate path may be extended facilitating redundancy and enablingmulti-path network coding to extend at the IP packet level.

In some embodiments, the motors (e.g., stepper motors) of the motor unit222 are controlled by a microcontroller unit (MCU) on the IDU 204. Inone example, the motor unit 222 is capable of moving the EHF module 220to enable a 75 degree rotation or more in the azimuth direction and a+25 degree rotation or more in the elevation direction.

FIG. 3A shows an example of a MDN endpoint node located on a roof top ofan apartment building (e.g., MDU 106). The MDN will communicate with theaggregation node 102 via high frequency links and couples with theswitches (e.g., SW) to provide connectivity to each of the apartments inthe apartment building 106.

FIG. 3B is a diagram of the enclosure mechanical arrangement of anexemplary MDN. The MDN includes similar components to the subscribernode 104. In particular, FIG. 3B depicts an EHF module 310 for theMDNa-1 with a number of patch array antennas 320 for high frequencycommunication with the aggregation node 102. These antennas are notactively steered, but a couple of separate patch array antennas areconnected in parallel to increase gain, in this specific embodiment. Inother embodiments, however, mechanically or electrically steeredantennas are used.

FIG. 4A is a block diagram of the endpoint node 104, with its componentsor modules. The components are arranged between the DU 204, bridge unit206 and ODU 202. In this way, it is illustrative of the subscriberendpoint node discussed in FIG. 2A-2C. That said the electronicconstruction is relevant to the MDU endpoint unit discussed in FIGS. 3Aand 3B.

In more detail, the IDU 204 contains electronic circuits, primarily ontwo printed circuit board assemblies (PCBAs) referred to as a Win modemmodule 404 and a diplexer module 402.

According to some embodiments, the WiFi modem module 404 is a printedcircuit board assembly, which includes: 1) a 802.11ac 4×4 radio chipsetfor the internet (referred to herein as internet WiFi chipset 410), 2) a802.11ac n×n chipset, such as, (3×3) radio chip set (referred to hereinas local WiFi chipset 412 or local wireless module 210) for establishinga wireless data connection to a wireless router or access point 414 viaWiFi antennas 416 on the IDU 204, and 3) and a Bluetooth low energy(BLE) radio 418 for system configuration. Preferably, the modem module404 also include one or more wired and or optical network jacks such anoptical data connections or RJ-45 jacks.

In one embodiment, off-the-shelf printed circuit board assemblies(PCBAs) are used for the WiFi modem module 404 e.g., AP148 with 2 radioPCIe (Peripheral Component Interconnect Express) modules. In someembodiments, the local WiFi chipset 412 is mounted directly on the mainPCB without interconnections through inter-board connectors. In someembodiments, a QCA9980 PCIe card that has a ˜5 GHz operating frequencyis used for the internet chipset 410.

The diplexer module 402 includes a frequency diplexer for WiFi signals(e.g., 802.11ac signals) from the internet WiFi chipset 410 of the modemmodule 404, clock sources for low frequency local oscillator (LO)signals, a global positioning system (GPS) receiver 403, a 100 MHzreference synthesizer, and a microcontroller for managing variousfunctions, e.g., local functions, functions of the EHF module 220, andgimbal functions of the servo controlled motor unit 222.

The diplexer module 402 communicates with the internet WiFi chipset 410and the EHF module 220 via the WiFi signals. The EHF module 220 isconfigured to: i) perform frequency conversions between intermediatefrequencies (IF), WiFi or near WiFi frequencies (associated with theWiFi signals from the diplexer module 402) and high frequencies, and ii)communicate with one or more aggregation nodes 102 at the highfrequencies.

The ODU 202 includes the EHF module 220 and the servo controlled motorunit 222. The ODU 202 contains circuitries for the high frequencyantennas, frequency conversion, amplifiers, and LNBs (low noise blockdown converters) on the EHF module 220. The LNB is a combination oflow-noise amplifier, frequency mixer, local oscillator and intermediatefrequency amplifier.

Extending through the bridge unit 206 are cables supporting two or moretransmit intermediate frequency connections TXIF and cables supportingtwo or more receive intermediate frequency connections RXIF, electricalconnections for control and status signals, power to the EHF module 220,and a motor control harness between the diplexer module 402 and theservo controlled motor unit 222.

In some implementations, the radio on the modem module 404 has a TXEnable control signal that is asserted while the radio is transmitting.The diplexer module 402 buffers this signal, and passes it along to theEHF module 220. In one embodiment, the radio on the modem module 404also has a RX Enable control signal that is used to control the RX pathof the SPDT (single pole double throw) switch between the radio and itsantenna. The diplexer module 402 buffers this signal and passes it alongto the EHF module 220.

In some implementations, T/R switches connect the unidirectionaltransmission lines on the diplexer module 402 to the bi-directionaltransmission lines used on the modem module 404.

FIG. 4B is a block diagram of the MDN version of the endpoint node. Thevarious component/modules of the MDN are similar to and perform the samefunctions as modules of the subscriber node 104 as described in FIG. 4A.Diplexer module 422 communicates with WiFi modem module 424 and the EHFmodule 426 via the WiFi signals (i.e., 802.11ac signals). The diplexermodule 422 includes a frequency diplexer for the WiFi signals from themodem module 424, clock sources for LO signals, GPS receiver 423, a 100MHz reference synthesizer, and a microcontroller for managing variousfunctions, e.g., functions of the EHF module 426, and gimbal functionsof the motor unit 428.

The EHF module 426 performs frequency conversions between WiFi/IFfrequencies and high frequencies and communicates with the aggregationnode 102 at the high frequencies. An optional motor unit 428 is used torotate the EHF module 426 so that patch array antennas associated withthe EHF module 426 can be aligned for communicating with the aggregationnode 102. Specifically, the motor unit 428 rotates the EHF module 426around the vertical axis or in an azimuth direction and further tips theEHF module 426 around a horizontal axis or in the elevation direction.This movement allows the patch array antennas of the RIF module 426 tobe pointed at the phased array antenna system 103 of the aggregationnode 102.

The modem module 424 of the MDU (e.g., MDU 106-1) couples to therouter/switch SW-1) via an Ethernet port 430, a PoE splitter 435, alightning protector 436 and a PoE injector 437. The PoE injector 437 isused to add PoE capability to existing cabling used in MDUs. Therouter/switch SW-1 couples to one or more G.hn switches e.g., 126-1,126-2, 126-3. Wired data connections are maintained between the G.hnswitch and WiFi router 110, where the WiFi router provides wirelessconnectivity for a number of network devices in a particular unit (e.g.,apartment) of the MDU.

FIG. 5 shows an exemplary frequency plan utilized for high frequencywireless communications between the aggregation node 102 and thesubscriber nodes 104. In the transmit direction, four RF WiFi signalsfrom the internet chipset 410 are translated to IF signals in the 2-3.5GHz range by the diplexer module 402 of the IDU 204, for example. In thereceive direction, the received high frequency signals are translated tothe IF signals at the EHF module 220.

In particular, in the transmit direction, 4 MIMO outputs of the internetWiFi chipset 410 are multiplexed and compressed to two signals using thefrequency plan. Specifically, at the diplexer module 402, two outputs(e.g., Tx1 and Tx2) are combined into IF1 signal and two additionaloutputs (e.g., Tx3 and Tx4) are combined into IF3 signal. At the EHFmodule 220, the IF1 signal is upconverted into a high frequency signalHF1 that is transmitted with a horizontal polarization (HTx) and the IF3signal is upconverted to a high frequency signal HF2 that is transmittedwith a vertical polarization (VTx). Similarly, in the receive directionand at the EHF module 220, received high frequency signals aredownconverted into IF signals IF2 and IF4. These IF signals areconverted to WiFi signals (e.g., Rx1, Rx2, Rx3, and Rx4) at the diplexermodule 402, where the WiFi signals can be decoded by the internet WiFichipset 410. Each signal path (transmit or receive) in the EHF module220 passes two simultaneous carriers (e.g., IF1, IF3 for transmit andIF2, IF4 for receive) via horizontal and vertical polarization, whereeach carrier contains 802.11ac modulation of bandwidths (either 100 MHzor 50 MHz in total).

FIGS. 6A and 6B depict a block diagram of an exemplary embodiment of thediplexer module 402 of the MU 204. In the transmit direction, multispatial stream WiFi signals (e.g., four RF signals—Tx1, Tx2, Tx3, andTx4, in the 5 GHz WiFi band) are received from the internet WiFi chipset410. These signals are down-converted using two local oscillator (LO)frequencies (IFLO1, IFLO2) and combined onto two signal streams (IF1,IF3). Tx1, Tx2, Tx3 and Tx4 have carrier frequencies in the 5 GHz band.They are mixed with IFLO1, IFLO2 respectively followed by combining toyield diplexed signals IF1, IF3 with frequencies at 1.4 GHz and 2.1 GHz.

In more detail, as shown in FIG. 6A, Tx1, Tx2 signals from the internetWiFi chipset 410 are amplified in respective amplifiers 616. They arethen bandpass filtered by respective bandpass filters 618 to remove anyout of band interference. Tx1, Tx2 are then respectively mixed withlocal oscillator (LO) frequencies (IFLO1, IFLO2) in the mixers 620. Insome embodiments, IFLO1 operates at 6.7 to 7.4 GHz, and IFLO2 operatesat 7.4-8.1 GHz. The outputs of the mixers 620 are filtered by respectivebandpass filters 622. These bandpass filters 622 pass the differencecomponents of the mixers 620.

A Y combiner 624 combines the outputs from the bandpass filters 622 toyield the signal IF1. A subsequent amplifier 626 and attenuator 628adjust the level of the signal IF1. The attenuator 628 is used forautomatic level control (ALC). There is programmable attenuation in eachtransmit (TX) path to provide the ALC function based on temperature andmeasured RF power from II-IF module 220. This function is performed bythe local microcontroller unit MCU 666 (including direct control of theattenuators 628).

As shown in FIG. 6B, Tx3, Tx4 signals from the internet WiFi chipset 410are similarly mixed and combined to produce IF3 using local oscillator(LO) frequencies (IFLO1, IFLO2) in the mixers 620. Attenuator 628 issimilarly used for the ALC function.

These two streams IF1 and IF3 are transmitted using differentpolarizations for diversity. These streams are sent to the EHF module220 for: i) up-conversion to high frequency signals, ii) amplification,and iii) wireless transmission to the aggregation node 102.

In the receive direction, two diplexed streams (IF2, IF4) are convertedinto multi spatial stream WiFi signals (e.g, four RF signals—Rx1, Rx2,Rx3 and Rx4) at the appropriate frequency for reception and decoding bythe internet WiFi chipset 410. Each receive path includes a splitter 640followed by two different band-pass filters 646, 648 followed byseparate mixers 652.

Consider IF2 signal as an example. As shown in FIG. 6A, IF2 signal isreceived at the diplexer module 402. The signal ranges between 1.4-2.8GHz in frequency. The signal is split in a Y splitter 640. Two digitalattenuators 642 are provided to adjust each divided signal.

Switches 644 for each receive path are used depending on the mode ofoperation. For example, if the signal quality of the link between theaggregation node 102 and the subscriber node 104 is low, then morerobust 40 MHz bandwidth channels are used. However, if the signalquality of the link is good/strong, then 80 MHz bandwidth modulation andchannels are used. In other examples, 160 MHz channels are used. A 40MHz bandwidth bandpass filter 646 is provided for each path. Inaddition, two 80 MHz bandwidth bandpass filters 648 are provideddepending on the type of modulation used. The four switches 644 are setbased on which of the two modulation modes is being used. The outputfrom the selected bandpass filters for each path is amplified in twoamplifiers 650.

The local oscillator (LO) frequencies (IFLO1, IFLO2) in the mixers 652convert the 1.4-2.8 GHz IF2 signal to the 5250-5350 MHz frequencies thatare expected by the Internet WiFi chipset 410. These 5 GHz frequenciesare then provided on Rx1 and Rx2 through amplifiers 656.

A similar series of components 640, 642, 644, 646, 648, 650, 652, 654,and 656 convert IF4 into Rx3 and Rx4, as shown in FIG. 6B.

In some embodiments, the local oscillator (LO) frequencies (IFLO1,IFLO2) used by mixers 620, 652 are generated from the GPS carriersignals using a synthesizer 670 (shown in FIG. 6B) on the diplexermodule 402. In one embodiment, a 1.5 GHz GPS signal is received from theEHF module 220. The GPS carrier is used to control/discipline a 100 MHzoscillator 407. This 100 MHz signal is used to synchronize the variousLO signals used on the diplexer module 402 and the EHF module 220. Insome embodiments, a GPS antenna (e.g., GPS antenna 403 of the diplexermodule 402 or other GPS antenna provided at the EHF module 220) isincluded that receives the 1.5 GHz GPS carrier.

The diplexer module 402 provides two LO signals (IFLO1, IFLO2)frequency-locked to the 100 MHz reference signal. In one embodiment, oneLO signal (e.g., IFLO1) is in the range of about 6.7-7.4 GHz, and theother LO signal (e.g., IFLO2) is equal to the first frequency plus 700MHz (i.e., IFLO2 is in the range of 7.4-8.1 GHz). This can be realizedin multiple ways including two fully independent synthesizers, as willbe appreciated.

In some implementations, the programmable attenuators 642 in each RXpath are controlled directly by the local MCU 666, under direction ofcentral processing unit (CPU) of the modem module 404. The CPU of themodem module 404 uses RSSI (received signal strength indicator)information from the radio to make adjustments to RX gain.

In some embodiments, the microcontroller (MCU) 666 is used to handle thereal-time management of the diplexer module 402, the EHF module 220, andGimbal functions of the motors associated with the motor unit 222. Inone implementation, the MCU 666 controls two servo motors associatedwith the motor unit 222. The motors are controlled in order to maximizethe received signal strength RSSI of the high frequency signals from theaggregation nodes.

FIG. 7 shows an embodiment where WiFi signals from the internet WiFichipset 410/modem module 404 are directly communicated to the EHF module220 without conversion to IF frequencies. On the transmit side, WiFisignals from a 2×2 WiFi 801.11 ac chipset are passed through anautomatic level control (ALC) attenuator 720 and amplifier 725 prior tobeing communicated to the EHF module 220 for up-conversion to highfrequency signals. On the receive side, at the EHF module 220, thereceived high frequency signals are down-converted to WiFi signals thatcan be decoded by the WiFi chip set 410. The WiFi signals from the EHFmodule 220 are amplified at amplifier 730. The amplified signals arepassed through a band pass filter 735 and an automatic gain control(AGC) attenuator 740 prior to being communicated to the WiFi chipset410. In some implementations, single pole double throw (SPDT) switches710 enable transmission or reception control (whether radios aretransmitting or receiving) based on Tx/Rx control signals from the WiFichipset 410.

FIGS. 8A and 8B show exemplary views of the EHF module 220 of the ODUunit 202. The EHF module 220 includes components for frequencyconversion between WiFi/IF frequencies and high frequencies, one or morepower amplifiers, a high frequency LO generation unit (from 100 MHz), aGPS antenna, transmission power detectors, and/or temperature sensors.

The EHF module 220 manages the high frequency communications for thesubscriber node 104. It contains transmit and receive antennas and allup and down frequency conversion circuitry. There are possibly two orthree printed circuit boards (PCBs): antenna PCB(s)/module 810 and RFcircuitry EHF PCB 812, as shown in FIG. 8B, in one example. These boardsare integrated into a brick-like assembly that is placed in the ODU 202and mounted on the servo controlled motor unit 222 to form a steerableantenna module.

As shown in FIG. 8B (from top to bottom of figure), the EHF module 220assembly includes:

1. Cover 806 that is transparent to the frequencies.

2. Waveguide Backshort, Top 808.

3. antenna PCB(s)/module 810.

4. Central Chassis 811.

5. EHF PCB 812.

6. Waveguide Backshort, Bottom 818.

7. Back Plate 814.

8. Heat Sink 816.

The EHF PCB 812 is completely enclosed in an aluminum housing formed bythe back plate 814 and the central chassis 811, except for provisionsfor cable entry. Connections between the antenna PCB(s)/module 810 andthe UHF PCB 812 are accomplished using waveguide channels integratedinto the central chassis component 811 as well as bottom aluminumbackshorts 818 affixed to the bottom surface of the EHF PCB 812 and topaluminum backshorts 808 on the top surface of the antenna PCB(s)/module810. The EHF PCB 812 contains all of the active circuitry used in theEHF module 506. The various circuits and their functions are describedbelow in detail with respect to FIGS. 9A and 9B.

Some of the characteristics of one embodiment of the antennaPCB(s)/module 810 include the following:

Operating frequency: 38.6 GHz-40.0 GHz,

Number of ports: 4 (2 for vertical polarization/2 for horizontalpolarization), and

3 dB beamwidth: 6 degrees (both in azimuth and elevation)

FIGS. 9A and 9B illustrate a block diagram depicting some of thecomponents of the EHF module 220 implemented on the EHF PCB 812, forexample.

1. Phase Locked Oscillator (PLO) or RFLO synthesizer 952 to create LOfrequency signals/RFLO synthesizer signals (for example, RFLO at 9.3GHz). In one embodiment, the 100 Megahertz signal received from thedisciplined 100 MHz clock generator 407 is converted to the RFLOsynthesizer signal by driving the RFLO synthesizer 952.

2. Two Tx paths with filtering (TxPath1, TxPath2).

3. Two Rx paths with image rejection (RxPath1, RxPath2).

4. Waveguide transitions 960, 964 to transmit antennas and waveguidetransitions 962, 966 from the receive antennas.

5. Track and Hold Power Detectors 918 on the outputs of the power amps916 to monitor Tx levels.

6. Power regulators 975 and/or inverters.

7. Microcontroller (MCU) 980 to monitor sensors, signal, and/or othercircuits.

8. GPS antenna 950, GPS amplifier 970, and GPS signal pass-through 972to the diplexer module 402.

The transmit paths (TxPath1, TxPath2), as depicted in FIG. 9A,correspond to two polarizations. Each transmit path receives an IFsignal (e.g., IF1 or IF3 in FIGS. 6A and 6B) from the diplexer module402. The IF signals are in the range of 1.4 GHz to 2.8 GHz. The IFsignals are up-converted to high frequency signals (e.g., in a range of38.6 GHz to 40 GHz) and amplified on the EHF PCB 812. Afteramplification, the signal waveguide transitions 960, 964 provide thesignals to the antenna PCB(s)/module 810 via a short section of thewaveguide.

Specifically, IF1 is received on to TxPath1. IF1 is mixed in a mixer 910with RFLO at 9.3 GHz, which is frequency quadrupled, in multiplier 912prior to mixing. The mixer output is amplified in amplifier 916. A powerdetector 918 detects the output power. The high frequency signal is thensent to the antenna PCB(s)/module 810 that transmits the high frequencysignal with a horizontal polarization HTx.

Similarly, IF3 is received onto TxPath2. It is also mixed in a mixer 910with RFLO at 9.3 GHz, which is frequency quadrupled in multiplier 912prior to mixing. The mixer output is amplified in amplifier 916. Asecond power detector 918 measures output power. The high frequencysignal is then sent to the antenna. PCB(s)/module 810 that transmits thehigh frequency signal with a vertical polarization VTx.

A temperature sensor 920 is placed in proximity to each of the transmitpaths TxPath1, TxPath2. The MCU 980 reads the monitored temperature thatcan be used for automatic level control (ALC) functions.

Each high frequency transmit path (TxPath 1, TxPath2) has a directionalcoupler 922 located immediately after the final power amplifier 916.Each directional coupler 922 feeds the respective power detector 918that converts the RF power to a DC voltage. The local MCU 980 performsADC conversion on the two DC signals associated with each transmit pathand calculates actual transmit power in dBm.

The two receive paths (RxPath1, RxPath2), as depicted in FIGS. 9A and9B, correspond to the two polarizations. Each receive signal (e.g., in arange of 38.6 GHz to 40 GHz) associated with the receive path isreceived from the antenna PCB(s)/module 810 via waveguide transitions962, 966. The receive signal passes through to an LNB for frequency downconversion. The resulting IF signal (e.g., in a range of about 1.400 to2.800 GHz) is transmitted over coax to the diplexer module 402.

In more detail, the HRx signal (i.e., high frequency signal withhorizontal receive polarization) associated with RxPath1 is amplified inan amplifier 930. A mixer 932 mixes the signal with RFLO at 9.3 GHzwhich is frequency quadrupled in multiplier 934 prior to mixing. Theresulting signal is sent through amplifier 936.

Similarly, the VRx signal (i.e., high frequency signal with verticalreceived polarization) associated with RxPath2 in amplified in amplifier930. Mixer 932 mixes the signal with RFLO at 9.3 GHz which is frequencyquadrupled in multiple 934 prior to mixing. The resulting signal is sentthrough amplifier 936.

In some embodiments, the signals obtained after amplification viaamplifier 936 in the two receive paths (RxPath1, RxPath2) correspond tothe IF2, IF4 signals, depicted in FIGS. 6A and 6B, that are transmittedto and received by the diplexer module 402.

The local MCU 980 performs management and status checking of the variouscomponents of the EHF module 220. The MCU 980 measures RF Transmit powervia the power detectors 918. In particular, two RF_POWER analog voltagesfrom the power detectors 918 are measured.

A serial (UART) connection is provided to the diplexer module 402 in theillustrated example. The MCU 980 detects, for each transmit path, theEHF temperature using temperature sensors 920. The temperatureinformation (and/or the power measurement information) can be used bythe diplexer module 402 to implement the automatic level control (ALC)via the programmable attenuators 628 of the diplexer module 402.

The MCU 980 can also manage the TX_ENABLE signal from the internet WiFichipset 610. The MCU 980 also monitors the synthesizer operation of theRFLO synthesizer 952 via a PLL Lock Status (digital input).

The local RFLO synthesizer 952 is synchronized to a 100 MHz referencesignal (which, in turn is GPS disciplined). The RFLO synthesizer signalis used for all four mixers 910, 932 (two on the transmit paths and twoon the receive paths) found on the EHF PCB 812.

The EHF PCB 812 has local voltage regulators and a single DC inputvoltage. Two power control inputs are provided to the EHF PCB 812. Theseinputs are used to power down the transmitters and/or receivers duringperiods when they are not needed (e.g., as decided by an outsidecontroller).

In some implementations, each transmit path receives WiFi signals (e.g.,WiFi1 and WiFi3) directly from the internet WiFi chipset 410 asdescribed in FIG. 7. In this scenario, the WiFi signals (e.g., in arange of 5250-5350 MHz) are up-converted to high frequency signals (inthe range of 38.6 GHz to 40 GHz) and amplified on the EHF PCB 812. Inparticular, on the transmit side, WiFi signals (WiFi1, WiFi3) are mixedin respective mixers 910 with RFLO signals (having an appropriatefrequency for WiFi to high frequency conversion), which are frequencyquadrupled, in multiplier 912 prior to mixing. The mixer outputs areamplified in respective amplifiers 916. The respective high frequencysignals (e.g., in a range of 38.6 GHz to 40 GHz) are then sent to theantenna PCB(s)'module 810 that transmits the high frequency signals withcorresponding horizontal and vertical polarizations HTx, VTx.

On the receive side, the high frequency signals associated with the twopolarizations are received from the antenna PCB(s)/module 810. Thesehigh frequency signals (e.g., in a range of 38.6 GHz to 40 GHz) aredown-converted to WiFi signals (e.g., in a range of 5250-5350 MHz)without IF conversion. In particular, the high frequency signalsassociated with the two receive paths (RxPath1, RxPath2) are amplifiedin respective amplifiers 930 and mixed in respective mixers 932 (wherethe signals are mixed with RFLO signals having an appropriate frequencyfor high frequency to WiFi conversion). The resulting signals areamplified in respective amplifiers 936 prior to communication to theinternet WiFi chipset 410.

FIGS. 10A and 10B depict exemplary patch antenna array modules 810.

FIG. 10A shows a first embodiment. Here, two 16×16 dual polarizedserially fed patch array antennas 1010, 1012, on respective circuitboards, are placed side by side. The antenna module 810 also includesthe GPS antenna 950.

The array columns of the patch array antennas 1010, 1012 can be excitedvia a feed network (which is not shown in the FIG. 10A). The overallsize of printed circuit board module is approximately 80×185 mm. Theantenna elements of each 16×16 patch array antenna 1010, 1012 areprinted on a substrate and the antenna output terminals are waveguidetransitions (e.g., waveguide transitions 960-966 depicted in FIGS. 9Aand 9B).

FIG. 10B shows a second embodiment of the antenna module 810. Here, thetwo 16×16 dual polarized serially fed patch array antennas 1010, 1012integrated on a single board substrate 1014 within the module 810.

FIG. 11A shows another example of a patch array antenna 1010, 1012.

FIG. 11B shows a cross-sectional view of exemplary material layers ofthe patch array antennas 1010, 1012. The topmost patch layer 1110 ispatterned with antenna patch elements of the patch array antennas 1010,1012. The copper weight utilized for the patch layer 1110 is 0.5 ounce(oz) copper. A ground layer 1116 is sandwiched between two dielectriclayers 1112 and 1118. The dielectric layer 1112 has 20 mils thicknessand the dielectric layer 1118 has 5 mils thickness. The copper weightutilized for the ground layer 1116 is 0.5 oz copper. A prepreg layer1114 (e.g., a fastRise™ prepreg of 1.9 mils thickness) is providedbetween the dielectric layer 1112 and the ground layer 1116 to eliminatedifferential skew. A feed layer 1120 includes the feeding network/feedlines of the patch array antennas 1010, 1012. The copper weight utilizedfor the feed layer 1120 is 0.5 oz copper.

For example, FIG. 12A depicts two 16×16 patch array antennas 1010, 1012being fed using a feeding network comprising feed lines 1202 in serieswith antenna patch elements.

FIG. 12B depicts two 16×16 patch array antennas 1010, 1012 being fedusing an aperture coupled feeding network such that fields on the feedlines 1204 (bottom layer) couples to the slots 1206 on the ground layer1116 and then couples to the antenna patch elements on the patch layer1110.

FIG. 13 shows the configuration in which the above two feedingtechniques of FIGS. 12A and 12B are combined to excite vertical andhorizontal polarized waves simultaneously for improved isolation. Forexample, the combined feeding technique at the EHF module 220/antennaPCB 810 can be used to transmit high frequency signals with horizontalpolarization HTx and vertical polarization VTx, simultaneously from theantennas 1010, 1012.

FIGS. 14A and 14B illustrate embodiments for coupling patch antennaarrays 320 (as shown in FIG. 3B) for a MDN (e.g., MDNa-1) of a MDU106-1, for example.

FIG. 14A illustrates two patch antenna arrays 1410, 1420, where eachpatch antenna array has two polarization inputs/ports 1415, 1416. Theports 1415, 1416 of the two patch antenna arrays 1410, 1420 are coupledto a feed plate 1430. FIG. 14B illustrates a mechanism for connecting asmall antenna with the big antenna using a distribution plate. Ports ofa feed plate 1430 (for the two patch antenna arrays) are coupled to adistribution plate 1450. The distribution plate 1450 splits/combineseach port by 4 and routes to a larger array. In particular, the outputsof the distribution plate 1450 couple to an array of 8 patch antennaarrays 320. Each port of the 8 patch antenna arrays 320 is coupled tothe distribution plate 1450.

FIGS. 15A and 15B illustrate renderings of sector heads of theaggregation node 102. In particular, FIG. 15A illustrates a 120-degreesector head aggregation node 102, and FIG. 15B illustrates a3-sectorhead aggregation node 102 (without mounting hardware). Theaggregation node 102 can be located on a roof top or other verticalassets or locations suitable for transmitting and receiving highfrequency signals to and from multiple subscriber nodes 104.

In general, the aggregation nodes 102 are installed at locations similarto where cellular phone base station antennas are installed. Preferably,this would be a high point in a city or town or neighborhood. This pointwould provide open line-of-sight or near open line-of-sight path to eachof the subscriber nodes 104.

In still another embodiment, the aggregation nodes 102 are mounted ontop of telephone poles at the neighborhood level. In contrast, incities, the aggregation nodes 102 in some cases are installed on tallbuildings within neighborhoods. In the case of apartment buildings andpossibly multiple apartment buildings, the aggregation nodes 102 can bepositioned to have good line of sight access down streets so that therewould be line of sight paths to subscriber nodes 104 installed as windowunits in each apartment in large apartment buildings.

FIG. 16 illustrates two deployment examples for the aggregation node102. The first example corresponds to a multi-sector deployment for theaggregation node 102 and the second example corresponds to a singlesector deployment for the aggregation node 102. In either deploymentexample, the sector head(s) 1602 contains the bulk of the circuitry anddevices that are used in the aggregation node 102, which are provided inan enclosure. For example, the sector head(s) 1602 can include RFcircuitry, modern circuitry, networking circuitry, DC power input, smallform-factor pluggable modules (SFP+, SFP) and RS232 ports.

The multi-sector deployment of the aggregation node 102 illustratesthree sector heads 1602-1, 1602-2, and 1602-3 coupled to a multi-sectoradaptor 1604. Power and network cables are run between each sector head1602-1, 1602-2, 1602-3 and the multi-sector adaptor 1604. In someembodiments, the multi-sector adaptor 1604 provides power and networkingsupport to two or more sector heads. The multi-sector adaptor 1604functions as a power/network aggregator for the sector heads 1602-1,1602-2, and 1602-3. The multi-sector adaptor 1604 includes AC powerinput, DC power output, and small form-factor pluggable modules (e.g.SFP+ for the Internet and sector heads, and SFP for service).

In the single-sector deployment, a single sector head 1602 is coupled toa single sector adaptor 1606 that provides power to the single sectorhead 1602.

FIG. 17 depicts components of an exemplary sector head 1602 in moredetail. The sector head 1602 includes circuitry for performingconversions between i) WiFi and IF frequencies, and ii) IF and highfrequencies. In particular, the sector head 1602 includes the followingcomponents and functions:

1) SH modem block 1702 includes 802.11ac radios (transceivers) chipsets,network processor(s), network interfaces, and system control circuitry.

2) SH diplexer block 1704 includes circuitry for performing up/downfrequency conversion (i.e., WiFi to IF conversion and vice versa),duplexing, and filtering. The SH diplexer block 1804 also contains a LOnetwork for distributing LO signals.

3) SH RIF block 1706 includes high frequency up/down converters (forperforming IF to high frequency conversion and vice versa), beam formingnetwork, RF switches, power amplifiers, LNBs, antennas, and a LO networkfor distributing LO signals.

4) SH LO generators block 1708 include high fidelity clock sources forup/down frequency conversion, where a GPS carrier is used to disciplinea 100 MHz oscillator. The SH LO generators 1708 includes 3 clocksources, 3 agile oscillators and 1 fixed oscillator. The SH LOgenerators block 1708 generates IFLO signals for WiFi—IF conversion andRFLO signals for IF—high frequency conversion.

5) SH power system 1710 that includes DC power supplies and filtering asrequired for the other component blocks.

FIG. 18 illustrates an exemplary schematic for the aggregation node 102that utilizes the phased array antenna system 103T, 103R to communicatewith multiple subscriber nodes 104, where the phased array antennasystem 103 divides an area of coverage into multiple subsectors. Thisaggregation node 102 uses a frequency plan as discussed in connectionwith FIG. 5.

The embodiment leverages multiuser MIMO WiFi chipsets (mu-MIMO) thatimplement the IEEE 802.11ac version of the standard and follow-onversions. Multi-user MIMO (mu-MIMO) relies on spatially distributedtransmission resources. In particular, mu-MIMO WiFi chipsets encodeinformation into and decode information from multi spatial stream WiFisignals associated with multiple users.

Considering the transmission side/path, data to be transmitted (e.g.,data from a fiber coaxial backhaul) is provided to two 4-port mu-MIMOWiFi chipsets 1810 a, 1810 b. These chipsets are implemented on a modemboard at the SH modem block 1702.

The WiFi chipsets 1810 a, 1810 b produce eight 5 to 6 GHz WiFi signalsthat are output on two signal paths Tx1, Tx2 (i.e., 4 WiFi signals onTx1 and other 4 WiFi signals on Tx2). The WiFi sign re provided to twotransmit diplexers 1812 a, 1812 b of the SH diplexer block 1704.

Each of the two transmit diplexers 1812 a, 1812 b uses fixed localoscillator signals (IFLO1, IFLO2, IFLO3, IFLO4) to down-convert the 5 to6 GHz WiFi signals to intermediate frequency (IF) signals (IF1, IF2,IF3, IF4) in a range of 2 to 3 GHz. In some implementations, the IFLOsignals are in the range of 7.8-8.2 GHz.

At each transmit diplexer, IF1 and IF2 signals are combined(summed/added) to form one IF signal, and IF3 and IF4 signals arecombined to form another IF signal. In this way, the WiFi signal aremultiplexed into IF signals. Preferably the IF signals are offset byover 100 MHz, such as by 700 MHz.

These combined IF signals from the two diplexers 1812 a, 1812 b areprovided to four block-up convertors (BUCs) 1814 a, 1814 b, 1814 c, 1814d.

The BUCs 1814 a, 1814 b, 1814 c, 1814 d upconvert the combined IFsignals to high frequency signals. The upconverted IF signals areprovided as inputs to a phase control device that includes one or more8-port Rotman lens 1816 a, 1816 b, in this specific implementation. Thephase control device is configured to feed the transmit phased arrayantenna system 103T (e.g., transmit antenna arrays 1820 a, 1820 b of thephased array antenna system) via a set of feedlines 1819 a, 1819 b. Inparticular, Rotman lens 1816 a feeds a horizontal polarization transmitantenna array 1820 a and Rotman lens 1816 b feeds a verticalpolarization transmit antenna array 1820 b. In some implementations, theupconverted IF signals are combined at a combiner associated with eachRotman lens 1816 a, 1816 b.

The Rotman lens 1816 a, 1816 b vary phases of the upconverted highfrequency signals to, in combination with the transmit antenna arrays1820 a, 1820 b, steer the high frequency signals towards one or moresubsectors in the area of coverage. Specifically, the upconvertedsignals are directed to different ports of the Rotman lens 1816 a, 1816b. The Rotman lens 1816 a, 1816 b control phases of the upconvertedsignals to be fed to an amplifier system and then to the transmitantenna arrays 1820 a, 1820 b. The amplifier system includes poweramplifiers 1818 a, 1818 b provided at output ports of the Rotman lens1816 a, 1816 b. The amplifier system amplifies the feeds on thefeedlines 1819 a, 1819 b to the transmit antenna arrays 1820 a, 1820 b.

The BUCs 1814 a, 1814 b, 1814 c, 1814 d use a first frequency localoscillator signal RFLO1 or a second frequency local oscillator signalRFLO2 that are frequency shifted from each other by 380 MHz. These localoscillator signals are utilized to convert the IF signals received fromthe diplexers 1812 a, 1812 b to the high frequency signals fortransmission. The center frequencies of the high frequency signals,however, are shifted with respect to each other.

In more detail, BUCs 1814 a, 1814 c receive RFLO1 and BUCs 1814 b, 1814d receive RFLO2. This arrangement results in the two WiFi chips setsoperating at different center frequencies that are shifted with respectto each other in the high frequency signals for transmission. Thisoccurs because the 4 Tx1 signals from the first WiFi chipset 1810 a arerouted from the TX diplexer 1812 b to BUCs 1814 b, 1814 d. In contrast,the 4 Tx2 signals from the second WiFi chipset 1810 b are routed fromthe TX diplexer 1812 a and to BUCs 1814 a, 1814 c.

A 100 megahertz signal received from GPS disciplined 100 MHz clockgenerator 1870 is converted to RFLO synthesizer signals (RFLO1, RFLO2)by driving a synthesizer module 1880. Preferably, generator module 1870and the synthesizer module 1880 also generate the IFLO signals used bythe transmit diplexers 1812 a, 1812 b to convert WiFi signals to IFsignals. In some implementations, the modules 1870 and 1880 are part ofthe SH LO generators block 1708.

The output ports of each of the two Rotman lenses 1816 a, 1816 b feedinto eight parallel amplifiers 1818 a, 1818 b for each antenna array1820 a, 1820 b. These eight amplifiers 1818 a, 1818 b for each of theRotman lenses 1816 a, 1816 b feed into the two 8×16 antenna arrays 1820a and 1820 b. However, 8×8, 8×10, 8×12, 8×18 antenna arrays might otherise be selected depending on the link budget requirement.

One of the transmit antenna arrays 1820 a then transmits the highfrequency signals associated with Rotman lens 1816 a with a horizontalpolarization and the other transmit antenna array 1820 b transmits thehigh frequency signals associated with Rotman lens 1816 b with avertical polarization. The polarization diversity can be achieved byadding a polarizing sheet in front of one of the antennas to rotate itsemissions.

On the receive side/path, two 8×16 receive antenna arrays 1840 a, 1840 bof the receive phased array antenna system 103R are provided. 8×8, 8×10,8×12, 8×18 antenna arrays might be used in the alternative, however.Antenna array 1840 a operates at a horizontal polarization and the otherantenna array 1840 b operates at a vertical polarization. The eightoutput ports of each of the two antenna arrays 1840 a, 1840 b feed intothe phase control device that includes one or more 8-port Rotman lens1842 a, 1842 b.

The Rotman lens phase control devices 1842 a, 1842 b receive highfrequency signals from one or more subsectors and/or differentdirections associated with the one or more subsectors simultaneously. Inparticular, Rotman lens 1842 a, 1842 b receives high frequency signalsat one or more of its input ports and controls the phases of thereceived signals to produce outputs to low noise block-down converters(LNBs) 1844 a, 1844 b, 1844 c, 1844 d, in which pairs of outputscorresponds to a unique subsector of the corresponding receive antennaarray 1840 a, 1840 b. Each of the two Rotman lenses 1842 a, 1842 bproduces two outputs that feed into two LNBs. For example, Rotman lens1842 a feeds into LNBs 1844 a, 1844 b, and Rotman lens 1842 b feeds intoLNBs 1844 c, 1844 d. Outputs from LNBs 1844 a and 1844 c (with differentpolarizations) correspond to one subsector and the outputs from LNBs1844 b and 1844 d (with different polarizations) correspond to anothersubsector.

The received high frequency signals at receive antenna arrays 1840 a,1840 b are combined at a combiner associated with each Rotman lens 1842a, 1842 b. The combiner vectorially sums the received high frequencysignals present at the antenna ports to be presented to one LNB input,such that each LNB 1844 a, 1844 b, 1844 c, 1844 d then receives oneformed beam. However, an alternative method of beam forming can beutilized where each signal is provided to the LNB and the outputs fromthe LNB can be summed to form a beam.

The LNBs 1844 a, 1844 b, 1844 c, 1844 d also use the local oscillatorsignals RFLO1 and RFLO2 generated by the synthesizer module 1880 forconverting the high frequency signals received at the antenna arrays1840 a, 1840 b to IF signals. Each subsector is handled by only one ofthe WiFi chipsets 1810 a or 1810 b, and also operates at a differentcenter in the high frequencies. LNBs 1844 a and 1844 c receive RFLO1. Incontrast, LNBs 1844 b and 1844 d receive RFLO2. As a result, despite theWiFi signals from two WiFi chipsets being upconverted and transmittingat different high frequency center frequencies, they are down-convertedto the same If frequencies.

The four low noise block-down converters 1844 a, 1844 b, 1844 c, 1844 dfeed into two receive diplexers 1846 a, 1846 b of the SH diplexer block1704. The inputs to the diplexers 1846 a, 1846 b are the IF signals of 2to 3 GHz. The diplexer demultiplexs the two offset signals in each IFsignal. Specifically, receive diplexer 1846 a produces four Rx2 WMsignals that will be processed by the second mu-MIMO WiFi chipset 1810b. In contrast, receive diplexer 1846 b produces four Rx1 WiFi signalsthat will be processed by the first mu-MIMO WiFi chipset 1810 a.

In some implementations, the block-up converters, the block-downconverters, the Rotman lens on the transmit and receive side, theamplifiers on the transmit side, and the antenna arrays on the transmitand receive side are part of the SH EHF block 1706 discussed withreference to FIG. 17, for example.

FIG. 19 is an exemplary block diagram of the SH modem block 1702 usedfor the embodiment described in FIG. 18. The SH modem block 1702 canimplement a radio/processor architecture based on QCOM AP148 design, orother commercial AP design, such as by Marvell Semiconductor, Inc. TheSH modem block 1702 includes the following components and functions.

1) 1904: Two units of 4×4 802.11ac 4×4 MIMO) Primary Radios 1810 a, 1810b with TX, RX, and PDET signals connected to coax connectors. ThePrimary Radios 1810 a, 1810 b (also referred to as WiFi chipsets herein)produce WiFi signals that are encoded according to the 802.11ac wirelessnetworking standard. The two units of Primary Radios 1810 a, 1810 b arecollectively configured to transmit/receive eight 5-6 GHz WiFi signals.In some embodiments, QCA9980 or Marvell 8964 can be used. The PrimaryRadios 1810 a, 1810 b are multiuser MIMO WiFi chipsets thatencode/decode information associated with multiple users in multiplespatial streams. In other words, the WiFi signals carry informationassociated with multiple users simultaneously. While the currentimplementations utilizes the 802.11ac standard, other subsequentwireless networking standards in the 802.11 family can be employed toprovide multiple spatial stream WiFi signals associated with multipleusers using multiple antennas, as would be appreciated. Furthermore,while WiFi signals in the 5-6 GHz frequency band (according to the802.11ac standard) are utilized by the current implementations, WiFisignals in other frequency bands associated with other standards in the802.11 family can be used.

2) One 4×4 802.11ac 4×4 MIMO) Secondary Radio 1906 for dedicated use asa spectrum analyzer. RX inputs are shared (divided) with the primaryradios 1904. In some embodiments, QCA9980 or Marvell 8964 can be used.

3) A first Network Processor 1908 configured to provide processingcapabilities for the various functions of the SH modem block 1702. Insome embodiments, IPQ8064, which is a Qualcomm Technologies, Inc.internet processor, but another network processor can be used.

4) Auxiliary network processor 1910 is used for system control, andconnects to the Ethernet (ETH) switch 1912. In some embodiments,IPQ8064, or other network processor can be used.

5) ETH Switch 1912 is coupled to fiber optic or copper networking cablesvia small form factor pluggable transceivers (SPF).

6) Power System 1914 with input voltage at 12V, and all necessary railsare generated on-board.

The physical interfaces of the SH modem block 1702 include varioussockets, connectors and ports, as well as inputs/outputs from amicrocontroller unit (MCU) 1916 that are used to control other modulesin the sector head 1602, such as SH EHF block 1706, SH diplexer block1704, and SH LO generators block 1708. In some implementations, the SRmodem block 1702 is provided inside an EMI/EMC enclosure.

FIG. 20 illustrates a block diagram of a transmit diplexer (for example,Tx diplexer 1812 a, 1812 b of FIG. 18) of diplexer block 1704, accordingto one embodiment. Four RF/WiFi signals are received at transmitdiplexer 1812 a from the modem block 1702. In particular, transmitdiplexer 1812 a receives four multi spatial stream WiFi signals from the4-port transmit mu-MIMO WiFi chipset 1810 a. The four WiFi signalsreceived have carrier frequencies in the 5170 MHz-5650 MHz range. At thetransmit diplexer 1812 a, the four WiFi signals are down-converted usinglocal oscillator frequencies (IFLO2, IFLO4) to yield intermediatefrequency (IF) signals IF1, IF2, IF3, IF4.

In detail, at transmit diplexer (e.g., 1812 a), four WiFi signals (Tx2)from the second WiFi chipset 1810 b are amplified in respectiveamplifiers 2020. They are then bandpass filtered by respective bandpassfilters 2022 to remove any out of band interference. In mixers 2024, thefiltered signals are mixed with local oscillator frequencies (IFLO2,IFLO4) from the synthesizer module 1880 to generate the IF signals. Insome implementations, the IFLO signals operate in the range of 7.8-8.2GHz. The outputs of the mixers 2024 are filtered by respective bandpassfilters 2026. Amplifiers 2028 adjust the level of the intermediatefrequency signals IF1, IF2, IF3, IF4. In some implementations, theintermediate frequency signals are in the 2.510-2.680 GHz range. Here,the IF signals are combined to yield two outputs for the block-upconverters of FIG. 18. For example, IF1 and IF2 signals are combined atsummer 2030 to yield combined IF signal C-IF1 and IF3 and IF4 signalsare combined at summer 2030 to yield combined IF signal C-IF2. The twocombined IF signals are provided as input to the block-up converters,where the two combined IF signals are converted to high frequencysignals.

As will be appreciated, the transmit diplexer 1812 b includes the samecomponents as and functions in a manner similar to transmit diplexer1812 a. As such, the description of FIG. 20 applies to transmit diplexer1812 b, where the WiFi signals are mixed with local oscillatorfrequencies (IFLO1, IFLO3) at mixers 2024 to generate the IF signals.

FIG. 21 illustrates a block diagram of a receive diplexer (e.g., Rxdiplexer 1846 a, 1846 b of FIG. 18) of diplexer block 1704, according toone embodiment. Two IF signals are received at receive diplexer 1846 afrom the LNBs of FIG. 18. The IF signals are converted into multispatial stream WiFi signals at the appropriate frequency for receptionand decoding by the mu-MIMO WiFi chipset 1810 b. In someimplementations, the IF signals are in the range of 2.510-2.680 GHz

In detail, at receive diplexer 1846 a, two IF signals are received fromthe LNBs. The two IF signals are split into four IF signals (IF1, IF2,IF3, IF4) at splitter 2105. The four IF signals are the converted tofour WiFi signals (4 Rx1 for RX diplexer 1846 a, 4 Rx2 for RX Diplexer1846 b). Each IF signal goes through similar processing to yield thecorresponding WiFi signals. The processing for the IF1 signal isdescribed below, however, the same description applies to other IFsignals (IF2, IF3, IF4) as well.

Considering the IF1 signal switches 2110 switch the IF1 signal dependingon the mode of operation. For example, if the signal quality of the linkbetween the aggregation node 102 and subscriber node(s) 104 is low, thenmore robust 40 MHz bandwidth channels are used. Depending on the signalquality of the link, 80 MHz or 160 MHz bandwidth modulation and channelsare used. The switches 2110 are set based on which of the modulationmodes/schemes. Bandpass filters 2120 are provided for the respective themodulation scheme used. The output from the selected bandpass filter2120 is amplified at amplifier 2130.

In some implementations, power detector 2124 measures the power of thesignal output from the selected bandpass filter 2120. Programmableattenuation is provided by attenuator 2125 based on the measured power.

Output from the amplifier 2130 is provided to mixer 2140 that convertsthe IF1 signal to a WiFi signal in the 5 GHz frequency range that isexpected by the modem block 1702. The mixer 2140 mixes the IF1 signalwith IFLO2 from the synthesizer module 1880 to generate the WiFi signal.The signal is passed through filter 2150 and attenuator 2160, andamplified by amplifier 2170 prior to being provided as output Rx2-1 tothe WiFi chipset 1810 a.

Each of the other IF signals IF2, IF3, and IF4 for the receive diplexer1846 a pass through similar components described with respect to IF1signal to generate respective WiFi signals Rx2-2, Rx2-3, Rx2-4 for themodem block 1702. In particular, IF2 signal is mixed with IFLO2 togenerate WiFi signal Rx2-2, IF3 signal is mixed with IFLO4 to generateWiFi signal Rx2-3, and IF4 signal is mixed with IFLO4 to generate WiFisignal Rx2-4. As will be appreciated, the receive diplexer 1846 bincludes the same components as and functions in a manner similar toreceive diplexer 1846 a. As such, the description of FIG. 21 applies toreceive diplexer 1846 b, where the WiFi signals are mixed with localoscillator frequencies (IFLO1, IFLO3) at mixers 2140 to generate the IFsignals.

FIG. 22 depicts components of another embodiment of the sector head 1602in detail. The sector head 1602, in this embodiment, includes circuitryfor performing direct conversion between WiFi and high frequencies,without the intervening IF conversion. In particular, the sector head1602 includes the following components and functions:

1) SH modem block 2202 includes 802.11ac radios (transceivers), networkprocessor(s), network interfaces, and system control circuitry. Thecomponents of the SH modem block 2202 are similar to the modem block1702, except that two units of 8×8 802.11ac (i.e., 8×8 MIMO) PrimaryRadios or WiFi chipsets are used (as described below with respect toFIG. 23).

2) SH EHF block 2204 includes high frequency up/down converters (forperforming WiFi to high frequency conversion and vice versa), beamforming network, RF switches, power amplifiers, LNBs, antennas, and a LOnetwork for distributing LO signals.

3) SH LO generators block 2206 include high fidelity clock sources forup/down frequency conversion, where a GPS carrier is used to disciplinea 100 MHz oscillator. The SH LO generators block 2206 generates RFLOsignals for WiFi—high frequency conversion.

4) SH power system 2208 that includes DC power supplies and filtering asrequired for the other component blocks.

FIG. 23 shows an embodiment that leverages 8-port mu-MIMO WiFi chipsets2310 a, 2310 b implemented at the SH modem block 2202. Specifically, onthe transmit side, the 8-port mu-MIMO WiFi chipsets 2310 a, 2310 b feedinto four quad block-up convertors (BUCs) 2312 a, 2312 b, 2312 c, 2312d. The WiFi signals from the Win chipsets are fed directly to theblock-up converters without conversion to IF signals as in the case ofFIG. 18. The block-up converters 2312 a, 2312 c, use local oscillatorsignal RFLO1; the block-up converters 2312 b, 2312 d use localoscillator signals RFLO2. RFLO1 and RFLO2 are frequency shifted fromeach other by 380 MHz).

The four quad block-up convertors (BUCs) 2312 a, 2312 b, 2312 c, 2312 dconvert WiFi signals to high frequency signals for transmission. Theoffset between RFLO1 and RFLO2 has the effect of offsetting the centerfrequency used to transmit and receive the high frequency signals usedfor the two mu-MIMO chipsets 2310 a, 2310 b with respect to each other.This reduces interference between the two chipsets.

In some implementations, a 100 megahertz signal received from GPSdisciplined 100 MHz clock generator 2370 is converted to RFLOsynthesizer signals (RFLO1, RFLO2) by driving a synthesizer module 2380.

Each BUC 2312 a, 2312 b, 2312 c, 2312 d produces four outputs. Two BUCs2312 a, 2312 b) provide eight inputs to a horizontal polarization Rotmanlens 2314 a. The other two BUCs (e.g., 2312 c, 2312 d) provide the eightinputs to the vertical polarization Rotman lens 2314 b. The Rotman lens2314 a, 2314 b form the transmit side phase control device thatfunctions in a manner similar to the phase control device of FIG. 18,except that each of the two Rotman lenses 2314 a, 2314 b receive eightinputs from the quad BUCs rather than two inputs.

The eight output ports of each of the two Rotman lenses 2314 a, 2314 bfeed into eight parallel amplifiers 2316 a, 2316 b for each antennaarray 2318 a, 2318 b. The power amplifiers 2316 a, 2316 b form theamplifier system that functions in a manner similar to the amplifiersystem of FIG. 18. The amplifiers should form a matched-set group, inthat they are factory aligned to be equivalent to each other withrespect to insertion gain (dBS21) and insertion phase (angS21). Theseeight amplifiers 2316 a, 2316 b for each of the Rotman lenses 2314 a,2314 b feed into two 8×16 antenna arrays 2318 a and 2318 b (i.e.,transmit antenna arrays of the phased array antenna system 103). Itshould be noted that 8×8, 8×10, 8×12, 8×18 arrays might be used,depending on the link budget requirements, to list a few examples. Oneof the transmit antenna arrays then transmits the high frequency signalsassociated with Rotman lens 2314 a with a horizontal polarization andthe other transmit antenna array 2318 b transmits the high frequencysignals associated with Rotman lens 2314 b with a vertical polarization.

The eight discrete inputs to each antenna array 2318 a, 2318 b, derivedfrom the four 5 GHz WiFi signals from each of two WiFi chipsets 2310 a,2310 b, result in eight subsectors that divide the 120 degree areacoverage for the antenna arrays 2318 a, 2318 b. The subsectors for eachof the antenna arrays 2318 a and 2318 b are coextensive with each otherbut separated by polarization. There is also frequency diversity betweenthe first four subsectors of each of the antenna arrays 2318 a, 2318 band the last four subsectors.

On the receive side, two 8×8 or 8×16 or other n'm receive antenna arrays2340 a, 2340 b of the phased array antenna system 103 are provided.Antenna array 2340 a operates at a horizontal polarization and the otherantenna array 2340 b operates at a vertical polarization. The eightoutput ports of each of the two antenna arrays 2340 a, 2340 b feed intotwo 8-port Rotman lens 2342 a, 2342 b. The Rotman lens 2342 a, 2342 bform the receive side phase control device that functions in a mannersimilar to the receive side phase control device of FIG. 18, except thateach of the two Rotman lenses 2342 a, 2342 b produce eight outputs thatyield eight subsectors that divide the 120 degree area coverage for thetwo receive antenna arrays 2340 a, 2340 b. Each of these outputscorresponds to one of the eight subsectors of the receive antenna arrays2340 a, 2340 b. These eight output feed into two 4-port (quad) low noiseblock-down converters (LNBs). For example, Rotman lens 2342 a feeds intoQuad LNBs 2344 a, 2344 b, and Rotman lens 2342 b feeds into Quad LNBs2344 c, 2344 d.

The Quad LNBs 2344 a, 2344 b, 2344 c, 2344 d use the local oscillatorsignals RFLO1 and RFLO2 for converting the high frequency signalsreceived at the antenna arrays 2340 a, 2340 b to WiFi signals that areexpected by/can be decoded by the two 8-port receive mu-MIMO chipsets2346 a, 2346 b of the modem block 2202. In some implementations, theblock-up converters, the block-down converters, the Rotman lens on thetransmit and receive side, the amplifiers on the transmit side, and theantenna arrays on the transmit and receive side are part of the SH EHFblock 2204.

Since the subsectors are assigned to different WiFi chipsets 2310 a,2310 b, they operate at different frequencies. As a result, quad LNBs2344 a, 2344 c, receive RFLO1; whereas quad LNBs 2344 b, 2344 d receiveRFLO2.

FIG. 24 illustrates a block diagram of a quad block-up converter (e.g.,Quad BUC 2312 a) of FIG. 23, according to one embodiment. Four WiFisignals are received at each QuadBUC 2312 a-2312 d from the modem block2202. In particular, each QuadBUC 2312 a-2312 d receives four multispatial stream WiFi signals from the 8-port mu-MIMO WiFi chipsets 2310a, 2310 b. The received WiFi signals have carrier frequencies in the51.70 MHz-5650 MHz range. At each QuadBUC 2312 a-2312 d, the four WiFisignals are up-converted using local oscillator frequencies (RFLO1,RFLO2) to yield high frequency signals RF1, RF2, RF3, RF4.

Considering QuadBUC 2312 a, the WiFi signals (Tx1-1 to Tx1-4) on eachpath 2401-2404 are amplified by respective amplifiers 2410. Theamplified signals are passed to respective digital attenuators 2412 foradjusting the level of the WiFi signals. In some implementations, theamplified signals in path 2401 and 2403 are phase adjusted prior tobeing passed to the digital attenuators 2412. After the signals arefiltered by channel filters 2414, the signals are mixed with oscillatorfrequency signals RFLO1 or RFLO2 (here RFLO1) at respective mixers M1-M4to upconvert the WiFi signals to high frequency signals. The RFLO1 andRFLO2 signals from the synthesizer module 1880 are distributed to thepaths 2401-2404 via LO network 2405. In some implementations, theoutputs of the mixers are filtered (by respective filters 2416) andamplified (by amplifiers 2418) prior to be being output as highfrequency signals RF1-RF4 to the Rotman lens (e.g., Rothman lens 2314a).

As will be appreciated, each QuadBUC 2312 b-2312 d includes the samecomponents as and functions in a manner similar to QuadBUC 2312 a. Assuch, the description of FIG. 24 applies to QuadBUCs 2312 b-2312 d aswell.

It will be understood that the QuadBUC described in FIG. 24 can also beutilized to implement alternate embodiments. For example, the QuadBUCcan be used to implement the embodiment described in FIG. 18 (e.g., BUCs1814 a-1814 d). In this embodiment, the QuadBUC is driven by one or moreIF signals instead of WiFi signals, where the IF signals areup-converted to high frequency signals. In some embodiments, the QuadBUCcan be driven by one IF signal. For example, one or more paths 2401,2402 can be driven by the IF signal (e.g., IF1/C-IF1). In otherembodiments, the QuadBUC can be driven by two or more IF signals, aswill be appreciated. This operation is achieved by control of the twoswitches S1, S2.

FIG. 25 illustrates a block diagram of a quad block-down converter(e.g., Quad LNB 2344 a) of FIG. 23, according to one embodiment. Fourhigh frequency signals (RF1-RF4) are received at each QuadLNB 2344a-2344 d from Rotman lens 2342 a, 2342 b. At each QuadLNB 2344 a-2344 d,the four high frequency signals are down-converted using localoscillator frequencies (RFLO1 or RFLO2) to yield WiFi signals that canbe decoded by the 8-port receive mu-MIMO chipsets 2346 a, 2346 b.

Considering QuadLNB 2344 a, the high frequency signals (RF1-RF4) on eachpath 2501-2504 are amplified by respective amplifiers 2510 prior tobeing mixed with oscillator frequency signals RFLO1. The amplifiedsignals are mixed with RFLO1 at respective mixers 2520 to downconvertthe high frequency signals to the WiFi signals (Rx1-1-Rx1-4). The RFLO1and RFLO2 signals from the synthesizer module 2380 are distributed tothe paths 2501-2504 via LO network 2505, that controls which of RFLO1and RFLO2 is used for the LNB and further conditions the signals. TheWiFi signals are filtered (by bandpass filters 2530), amplified (byamplifiers 2540), and phase adjusted (by phase shifters 2550) prior tobeing output to the WiFi chipset 2346 a.

As will be appreciated, each QuadLNB 2344 b-2344 d includes the samecomponents as and functions in a manner similar to QuadLNB 2344 a. Assuch, the description of FIG. 25 applies to QuadLNBs 2344 b-2344 d aswell.

It will be understood that the QuadLNB described in FIG. 25 can also beutilized to implement alternate embodiments. For example, the QuadLNBcan be used to implement the embodiment described in FIG. 18 (e.g., LNBs1844 a, 1844 h, 1844 c, 1844 d). In this embodiment, the QuadLNB outputsone or more IF signals instead of WiFi signals, where the IF signals areup-converted to WiFi signals. In some embodiments, the QuadLNB can bedriven by one high frequency signal (RFD. For example, path 2501 can bedriven by RF1 (i.e., the formed beam of FIG. 18) to generate one IFsignal (e.g., IF1) that is provided as input to receive diplexer 1846 a.In other embodiments, the QuadLNB can be driven by two or more RFsignals to generate two or more IF signals, as will be appreciated.

FIG. 26 illustrates a block diagram of the clock generator and thesynthesizer module of the SH LO generators block 1708, 2206, accordingto one embodiment. A GPS signal (operating at approximately 1.5 GHz) isused to control/discipline a 100 MHz clock generator 2610 (includingclock generators 1870, 2370). The 100 MHz reference signal from theclock generator 2610 is used by synthesizer module 2620 (includingsynthesizer modules 1880, 2380) to generate various LO signals that areused by transmit and receive diplexers, block-up converters, andblock-down converters (depicted in FIGS. 18 and 23, for example). Directdigital synthesizers 2640 of the synthesizer module 2620 are used togenerate the LO signals (IFLO1, IFLO2, RFLO1, and RFLO2) based on the100 MHz reference signal. In some implementations, IFLO1 and IFLO2signals operating at 7.9-8.3 GHz frequencies are generated for thetransmit and receive diplexers of FIG. 18. The RFLO1 and RFLO2 signalsoperating at 8.8 GHz-9.4 GHz frequencies are generated for the BM andLNBs of FIG. 18, and the QuadBUCs and QuadLNBs of FIG. 23. While FIG. 22depicts two IFLO signals (IFLO1 and IFLO2) being generated, it will beappreciated that additional IFLO signals (e.g., IFLO3 and IFLO4 depictedin FIG. 18) can also be generated based on the 100 MHz reference signal.

FIG. 27 shows the layout of the sector head including the antenna arraysused at the aggregation node 102. Two receive (Rx) antenna arrays (e.g.,1840 a, 1840 b of FIG. 18 or 2340 a, 2340 b of FIG. 23) and two transmit(Tx) antenna arrays (e.g., 1820 a, 1820 b of FIG. 18 or 2318 a, 2318 bof FIG. 23) are layout in a 2 by 2 array. Each transmit antenna arraysis coupled to the respective amplifier system 2722 comprising poweramplifiers (e.g., 1818 a, 1818 b of FIG. 18 or 2316 a, 2316 b of FIG.23). Each receive antenna array is a slotted waveguide antenna arraythat has an integrated phase control device ( ). Each transmit antennaarray is coupled to a separate phase control device. These phase controldevices control the phase of the high frequency signals beingtransmitted from or received at the antenna arrays, thereby making theantenna arrays phased antenna arrays.

FIGS. 28A and 28B depict an exemplary receive antenna array (e.g.,antenna array 2340 a) and its associated frontplate 2810. High frequencysignals from endpoint nodes 104 are received at antenna apertures orslots 2830 of the receive antenna array 2340 a. These slots are arrangedin a 8×8 array, in illustrated embodiment, although 8×8, 8×10, 8×12,8×16, and 8×18 arrays are possible depending on the link budgetrequirements. The signals feed into integrated Rotman lens 2342 a viafeedlines 2825. Outputs from the Rotman lens 2342 a are provided to LNBs(e.g., QuadLNBs 2344 a-2344 b of FIG. 23) via feedlines 2826. Thereceive antenna arrays 2340 b, 1840 a, and 1840 b (described withrespect to FIGS. 18 and 23) are implemented in the same manner asreceive antenna array 2340 a. The receive antenna arrays 2340 a, 2340 bwith their integrated Rotman lenses 2342 a, 2342 b form the receive sideof the phased array antenna system 103 in FIG. 23. Similarly, thereceive antenna arrays 1840 a, 1840 b with their integrated Rotmanlenses 1842 a, 1842 b form the receive side of the phased array antennasystem 103 in FIG. 18.

Transmit antenna arrays 2318 a, 2318 b, with their corresponding Rotmanlens 2314 a, 2314 b and power amplifiers 2316 a, 2316 b form thetransmit side of the phased array antenna system 103 of FIG. 23. FIGS.28C and 28D depict an assembly of components forming one part of thetransmit side of the phased array antenna system 103 of FIG. 23. Forexample, FIG. 28C shows the backplate of one transmit antenna array(e.g., antenna array 2318 a) coupled to the Rotman lens 2314 a via theamplifier system 2722. The amplifier system 2722 is an 8 channel poweramplifier assembly that includes 8 power amplifiers (e.g., 2316 a).Rotman lens 2314 a electronically steers the high frequency signals fromBUCs (e.g., QuadBUCs 2312 a-2312 b) by controlling the phase of the highfrequency signals. Signals from the BUCs 2312 a, 2312 b are fed to theRotman lens 2314 a via a 90 degrees waveguide bend 2846. The Rotman lens2314 a is configured to feed the transmit antenna array 2318 a viaantenna and waveguide feedlines 2845. Signals from the feedlines 2845are then emitted from antenna slots 2860 of frontplate 2850 associatedwith the transmit antenna array 2318 a. These slots are arranged in an8×8 array. This phase control by the Rotman lens 2314 a causes thesignals from the transmit antenna array 2318 a to be emitted as beams toparticular sub-sector(s) and/or specific endpoint node(s) 104. The highfrequency signals are amplified by the amplifier system 2722 prior totransmission. The transmit antenna arrays 2318 b, 1820 a, and 1820 b(described with respect to FIGS. 18 and 23) are implemented in the samemanner as transmit antenna array 2318 a.

The transmit antenna arrays yield a steerable beam in the azimuthdirection. That is, the beam can be steered by rotation around thez-axis and in the x-y plane. This is achieved by controlling the phaseof the signal emitted from each of the eight vertically extending(extending in the direction of the z-axis) columns of slots. On theother hand, the beam is pancaked in the z-axis or elevation direction.This is achieved by setting the phase of the signal emitted from therows of slots.

In the illustrated embodiments, the receive and transmit antenna arraysare slotted waveguide antenna arrays, where the antenna slots 2380, 2860are half wavelength long openings across the waveguide channel to createhorizontally polarized electromagnetic waves.

While the antenna slots 2830, 2860 associated with the receive andtransmit antenna arrays are depicted as 8×8 arrays, other size arrayscan be used depending on the link budget requirements. Different sizesof the same configuration like 8×8, 8×10, 8×12, 8×16, 8×18 can be used,such that the number of columns is often 8, but the number of rowsvaries. As the number of rows increase, more gain and directiveradiation pattern is achieved.

FIG. 29 illustrates a schematic diagram for high frequency transmissionat a transmit antenna array (e.g. antenna array 2318 a), according toone a different embodiment. In some implementations, a high frequencysignal (after up-conversion at a block-up converter) amplified at apre-amplifier 2902 and provided to a switch 2904. The switch 2904 can beconnected to any of the eight input ports of a Rotman lens 2314 a. Byvarying the phases of the signals propagating through the Rotmans lens2314 a, the direction of the overall signal output can be controlled (asdetermined by the constructive and destructive interferences of thesignals). Thus, a signal can be transmitted by a transmit antenna array2318 a of the phased antenna array system 103 and directed to particularsub-sector(s) and/or specific endpoint node(s) 104.

Power amplifiers 2316 a are provided at each output port of the Rotmanlens 2314 a for amplifying the signals. Although it is possible to havethe power amplifiers at the input ports of the Rotman lens 2314 a, theconfiguration of the power amplifiers at the lens output ports resultsin lower loss compared to the other configuration (i.e., poweramplifiers at lens inputs). Because these eight power amplifiers aremeant to be used as a matched-set group, they are to be factory alignedto be equivalent to each other with respect to insertion gain (dBS21)and insertion phase (angS21).

Electronic steering of a high frequency signal is performed by theRotman lens 2314 a, which couples the high frequency signal from any oneof the eight Rotman lens inputs to the corresponding transmittingantenna array.

While this invention has been particularly shown and described withreferences to preferred embodiments thereof, it will be understood bythose skilled in the art that various changes in form and details may bemade therein without departing from the scope of the inventionencompassed by the appended claims.

What is claimed is:
 1. An aggregation node for a wireless access system,the node comprising: two transmit phased array antennas and two receivephased array antennas for transmitting high frequency signals with ahorizontal polarization and a vertical polarization, respectively, toand receiving high frequency signals with a horizontal polarization anda vertical polarization, respectively, from subscriber nodes; Rotmanlenses coupled to each transmit phased array antenna and each receivephased array antenna via a set of feedlines; amplifiers for amplifyingthe feeds on the feedlines between the transmit phased array antennasand the Rotman lenses; and WiFi chipsets for providing WiFi signals toand receiving WiFi signals from the Rotman lenses via upconverters anddownconverters, wherein the upconverters upconvert the WiFi signalsprovided by the WiFi chipsets to the high frequency signals in afrequency range of 10 GHz to 300 GHz for transmission by the at leastone transmit phased array antenna and the downconverters downconvert thehigh frequency signals received by the at least one receive phased arrayantenna in the frequency range of 10 GHz to 300 GHz to the WiFi signalsreceived by the WiFi chipset.
 2. The aggregation node of claim 1,wherein the Rotman lenses control phases of signals to be fed to theamplifiers and then to the transmit phased array antennas to direct thehigh frequency signals to different portions of an area of coverage. 3.The aggregation node of claim 1, wherein the Rotman lenses controlphases of signals received from the receive phased array antennas todirect high frequency signals received from different portions of anarea of coverage to different output ports of the Rotman lenses.
 4. Theaggregation node of claim 1, wherein the Rotman lenses vary phases ofsignals to steer the signals towards one or more sectors in the area ofcoverage.
 5. The aggregation node of claim 1, wherein the amplifierscomprise power amplifiers provided at ports of the Rotman lenses.
 6. Theaggregation node of claim 5, wherein the power amplifiers are phasematched with respect to each other.
 7. The aggregation node of claim 1,further comprising a global positioning system antenna that receives aglobal positioning system signal that is used to generate a localoscillator signal that is used by the upconverters to upconvert the WiFisignals.
 8. A communication method for an aggregation node andsubscriber nodes in a wireless access system, the method comprising:generating high frequency signals for different subscriber nodes byupconverting WiFi signals from WiFi chipsets with upconverters thatupconvert the WiFi signals from the WiFi chipsets to the high frequencysignals in a frequency range of 10 GHz to 300 GHz; feeding the highfrequency signals into a transmit Rotman lens; amplifying feeds at theoutput ports of the transmit Rotman lens; and beaming the high frequencysignals to different subscriber nodes within an area of coverage withtwo transmit phased array antennas for transmitting high frequencysignals with a horizontal polarization and a vertical polarization,respectively; and receiving high frequency signals from the differentsubscriber nodes with two receive phased array antennas for receivingthe high frequency signals with a horizontal polarization and a verticalpolarization, respectively.
 9. The method of claim 8, furthercomprising: amplifying the high frequency signals received from thedifferent subscriber nodes; feeding the high frequency signals intoreceive Rotman lenses; and decoding the high frequency signals providedat the output ports of the receive Rotman lenses by downconverting thehigh frequency signals with downconverters that downconvert the highfrequency signals in the frequency range of 10 GHz to 300 GHz todown-converted signals and providing the down-converted signals to theWiFi chipsets.
 10. The method of claim 8, further comprising the Rotmanlenses controlling the phases of signals to direct the high frequencysignals to different portions of the area of coverage.
 11. The method ofclaim 8, further comprising receiving a global positioning system signalthat is used to generate a local oscillator signal that is used by theupconverters to upconvert the WiFi signals.